The received signal of k-th secondary user is represented by
y
k
(t)=
M
m=1
h
k
m
(t) ⊗ s
m
(t)+n
k
(t), (2)
where s
m
(t) and h
k
m
(t) represent the primary user’s trans-
mitting signal and the channel impulse response between
the primary user and the k-th secondary user on the m-th
subchannel, respectively. ⊗ denotes the convolution operator.
The noise n
k
(t) is assumed to be white Gaussian noise with
zero mean and power spectral density (PSD) σ
2
k
for the k-th
secondary user. Similar to the notes in [29], we operate an M
point discrete Fourier transform for the received signal y
k
(t).
We can use an M × 1 vector Y
k
to represent the received
signal on frequency-domain, which is given by
Y
k
=
M
m=1
h
k
m
s
m
+ n
k
, (3)
where denotes elementwise multiplication. h
k
m
, s
m
, and
n
k
are the discrete Fourier transforms of h
k
m
(t) s
m
(t) and
n
k
(t), respectively. We can construct a diagonal matrix H
k
m
=
diag(h
k
m
) and rewrite (3) in a matrix form, which is given by
Y
k
=
M
m=1
H
k
m
s
m
+ n
k
. (4)
Then the detection problem for each secondary user is to do
the following binary hypothesis test on M subchannels in
frequency domain, i.e.
H
k
0,m
: Y
k
= n
k
H
k
0,m
: Y
k
= H
k
m
s
m
+ n
k
, (5)
where m =1, 2, ..., M and k =1, 2, ..., K denote the m-th
subchannel and the k-th secondary user, respectively.
In a wideband wireless application, between two adjacent
spectrum sensing periods, it has a low probability that all
subchannels change their occupancy status, since spectrum
sensing is implemented in a relative short period (
e.g.
in 802.22
WRANs’ draft, it is supposed to carry out spectrum sensing
every 24.2 ms [22]). Then the spectrum occupancies between
two adjacent sensing periods are correlated, which offers us
the temporal redundancy information for compressed signal
reconstruction. On the other hand, the spectrum observations
of difference cooperative secondary users also have spatial
correlation which provides us spatial redundancy.
frequency
D
n-1=[ 0 0 1 0 0 1 1 0 0 ]
Dn =[ 1 0 1 0 0 1 0 0 0 ]
frequency
Fig. 2: An illustration of the spectrum temporal correlation
As illustrated in Figure 2, we define a general correlation
factor τ, which represents either the temporal or the spatial
correlation level, which is given by
τ 1 −
D
n
− D
n−1
M
. (6)
In section V, we will demonstrate that different correlation
levels provide different performance gains.
III. C
OMPRESSED SPECTRUM SENSING AND BAYE S I A N
LEARNING
In this section, we briefly introduce the compressed sensing
and Bayesian learning, thus providing the background for our
proposed ST-BCSS algorithm.
A. Compressed Sensing
Briefly speaking, compressed sensing solves an ill-posed
inverse problem. Given an N × 1 observation vector g and an
N × M (N<M) matrix Φ, M × M matrix Ψ, the task is to
find an M × 1 solution vector f to satisfy an equation, which
is given by
g =ΦΨf, (7)
where Φ is the compressed matrix and Ψ is the projection
matrix. The vector f has a sparse representation projected
by Ψ. When matrix Φ,Ψ and vector f satisfy the Restricted
Isometry Property (RIP) [6], it can be solved by following
optimization problem:
˜
f = arg min
˜
f
1
s.t. g =ΦΨ
˜
f. (8)
Compressed sensing based Analog-to-Information Conver-
sion (AIC) was proposed in [14] [21]. Eldar proposed a
blind wideband analog reconstruction method [17]. Based on
the autocorrelation reconstruction, [19] [30] [31] presented
a scheme of analog signal acquisition, which endows us
an implementation structure to acquire the wideband signal
within an affordable hardware cost. In this paper, based on
these implementation structures, we represent the analog signal
acquisition in a projection matrix, for simplicity. We construct
an N × M linear random sampling matrix A, to attain N
time domain samples from discrete received signal y
k
, which
is given by
g
k
= Ay
k
+
˜
n
k
, (9)
where A can be a Gaussian or Bernoulli random matrix and
the noise
˜
n
k
remains to be white Gaussian noise. In wideband
spectrum sensing, the vector y
k
can be represented sparsely
in the Fourier transformation domain, which is given by
y
k
= F
−1
w
k
, (10)
where F
−1
is the inverse Fourier transform matrix and w
k
is
the sparse representation. Substituting (10) into (9) we obtain
g
k
= AF
−1
w
k
+
˜
n
k
= Θw
k
+
˜
n
k
, (11)
where Θ = AF
−1
.
This full text paper was peer reviewed at the direction of IEEE Communications Society subject matter experts for publication in the IEEE DySPAN 2010 proceedings
Authorized licensed use limited to: SOUTH CENTRAL UNIVERSITY FOR NATIONALITIES. Downloaded on July 22,2010 at 09:42:42 UTC from IEEE Xplore. Restrictions apply.