超材料表面等离子体传输线与天线设计

需积分: 21 70 浏览量更新于2024-07-16 收藏 3.61MB PDF 举报

"这篇论文详细探讨了基于超材料表面等离子体（Spoof Surface Plasmon, SSP）的传输线和天线设计，提出了一种可靠且可重复的方法来实现SSP模式，并给出了等离子体结构的第一个等效电路模型。论文强调了在当前电子电路系统快速发展的背景下，解决集成电路紧凑性问题的重要性。SSP作为一种新型的高密度电子电路平台，具有传统电路无法比拟的高场特性，能为未来的电子和电磁系统提供新的解决方案。超材料是一种人工构造的物质，它通过设计单元结构的几何形状和尺寸，可以模拟出自然界不存在的电磁性质。表面等离子体是电磁波与导电介质表面的自由电子相互作用产生的波动现象，通常在金属表面出现。而Spoof Surface Plasmons则是模拟表面等离子体行为的一种人造结构，它们能在更宽的频率范围内工作，并且能够在非金属材料上产生类似等离子体的行为。论文中介绍的等离子体结构等效电路模型对于理解和设计基于SSP的电路至关重要。这个模型为电路设计师提供了理论指导，使他们能够在没有物理实验的情况下，预测和分析SSP模式在电路中的行为。这种方法的出现弥补了当前SSP电路设计缺乏系统化方法的空白。作者通过设计并实验评估了多种基于SSP的传输线、天线馈送网络和天线，展示了SSP技术在实际应用中的潜力。传输线的设计利用了SSP的高度场约束特性，能够减小线路尺寸而不牺牲性能。同时，SSP馈送网络和天线为天线设计提供了新的途径，尤其在高频和微型天线领域，SSP可能带来革命性的变化。此外，SSP不受传统电路紧凑性限制，这对于未来电子设备的小型化和集成化具有重大意义。这不仅有助于解决当前电子系统中空间限制的问题，也为无线通信、光电子学、传感器技术等领域开辟了新的研究方向。这篇博士论文通过深入研究和实验验证，强调了SSP在解决电子电路紧凑性问题上的潜力，以及其在新型高效电路和天线设计中的应用。对于新进入该领域的研究者和寻求特定问题背景信息的科学家来说，这是一份宝贵的资源，同时也认可了作者及其导师在该领域的杰出贡献。"

Fig. 2.5 The circuit model for symmetric SSP cells. a The equivalent

circuit model. b Comparison between dispersion curve results

from circuit model and eigen mode solver of CST Microwave

Studio. c The characteristic impedance of the symmetric

SSP cells

........................................... 20

Fig. 2.6 The circuit model for meander SSP cells. a One unit cell

of meander SSP structure. b The equivalent circuit model.

c The effective area for the equivalent capacitors. d The

effective area of the current paths for the equivalent

inductors

........................................... 21

Fig. 2.7 Meander SSP cells: dispersion curves and characteristic

impedance. The comparison between the dispersion results

of the SSP modes in meander cells calculated from equivalent

circuit model and full wave analysis for various a cell widths

and b cell period lengths. c The characteristic impedance

of the meander SSP cell

............................... 23

Fig. 2.8 Loading design for symmetric SW-TLs. a Current distribution

at the SW-TL. b Loaded SW-TL with two resistors. c Block

diagram representation of a loaded SW-TL. d The circuit

model for a loaded SSP cell

............................ 24

Fig. 2.9 Reﬂection results from loaded SW-TLs. a Circuit model

and b full wave simulation results. The loading resistors

for the four sets are tabulated in Table 2.4

................. 26

Fig. 3.1 Polarization transformation of mode converter. a The proposed

SSP structure connect ed to the mode converter to construct

the SW–TL. b The normal and c the azimuthal components

of the electric ﬁeld at six perpendicular planes to the mode

converter

........................................... 30

Fig. 3.2 Dispersion conversion. Inset The separate parts

of the mode converter

................................. 31

Fig. 3.3 Impedance matching of mode converter. a The proposed

mode converter for the meander SW-TL. b The effective area

for the equivalent capacitors. c Matching of the impedance

through the mode converter

............................. 32

Fig. 3.4 Mode converter design for U-shaped SSP cells. a The SSP

structure connected to the microstrip line via matching

transitions to build the SW-TL. b The speci ﬁed parameters

for the strip connector

................................. 33

Fig. 3.5 Mode converter design for U-shaped SSP cells. a The ground

regulator, b Simulated |S

| and c |S

| for ﬁve parameter sets

(Table 3.2) for the entire frequency range.

................. 35

Fig. 3.6 Effect of ground connector. a Surface current on the SW–TL

at 7 GHz, b Comparison of the S-parameter results (simulation)

of SW-TL with and without port connection

................ 36

xx List of Figures

Fig. 3.7 Mode convert er design for U-shaped SSP cells. a Substitution

of curved lines of the ground regulator by straight lines.

b S-parameter results of SW–TL with curved ground regulator,

straight ground regulator and SW–TL with parameters given

in Table 3.3. c S-parameter results for SW–TL wi th single, two,

three and four unit cells strip connectors

................... 37

Fig. 3.8 Experimental evaluation of U-shaped SW-TL. a The fabricated

prototype. b Comparison between the experimental

and simulation S-parameters results

....................... 38

Fig. 3.9 Mode converter design for symmetric SSP cells.

a The proposed compact design. b The conventional

mode converter

...................................... 39

Fig. 3.10 S-parameter results of symmetric SW-TL. a Simulated |S

for ﬁve parameter sets given in Table 3.4 as well as the SW-TL

with the conventional mode converter. b Experimental

evaluation of the design

............................... 40

Fig. 3.11 Meander SW-TL. a The schematic SW-TL. Inset the

dimensions of one SSP unit cell. b The simulated transmission

and reﬂection from the designed SW-TL

................... 41

Fig. 3.12 Loss in symmetric SW-TLs. a Comparison between |S

results for symmetric SW-TLs with different lengths.

b Simulation and measured insertion loss

of symmetric SW-TL

................................. 43

Fig. 3.13 Mutual coupling between SW-TLs. a The fabricated prototype

of the two closely located and loaded SW-TLs. Comparison

of the MC between SW-TLs and microstrip lines for various

b overlapping part lengths and c distance between

two SW-TLs

........................................ 44

Fig. 4.1 Resonance frequencies f

of cylindrical DRAs. Comparison

between f

of TE

01d

and HEM

11d

for various antenna

thicknesses

......................................... 48

Fig. 4.2 Field distribution of a cylindrical DRA. a The schematic

of an isolated DRA and the electric ﬁeld vector distributions

of the fundamental mode (TE

01d

). b The schematic of a DRA

on a ground plane and the electric ﬁeld vector distributions

of the nominal fundamental mode (HEM

11d

)................ 48

Fig. 4.3 The proposed meander SW-TLs. a The schematic

of the design. Inset The dimensions of one SSP unit cell.

b The magnetic ﬁeld distribution at two cutting planes

........ 50

Fig. 4.4 A DRA fed by SW-TL with four orientations. Arrows represent

the magnetic ﬁeld vectors. a The DRA’s axial direction

is parallel to the SW-TL. b The DRA is placed on top

of the SW-TL and its axial direction is parallel to the grooves

of the SSP cells. c The DRA is placed on top of the SW-TL

List of Figures xxi

and its axial direction is perpendicular to the SW-TL.

d The DRA is placed on top of the SW-TL and its axial

direction is parallel to the SW-TL

........................ 50

Fig. 4.5 A DRA fed by meander SW-TL. a The design con ﬁguration.

Inset: the simulated electric ﬁeld vector of the fundamental

mode TE

01d

and the feeding end. b A DRA fed by microstrip

transmission line. c The S-parameter results for various DRA

locations

........................................... 51

Fig. 4.6 Excitation of a cylindrical DRA. a Comparison

of S-parameter results among ﬁve cases: simulation

results for a DRA fed with the conventional microstrip

TL and with the SW-TL (T = 4 mm and T = 1.5 mm),

experimental results for a DRA fed with the SW-TL

(T = 4 mm). b Photographs of the fabricated SW-TL

feeding conﬁguration and the DRA

....................... 52

Fig. 4.7 Far ﬁeld radiation patterns of DRA (realised gain in dBi).

Comparison among three cases: Simulation results for the

conventional microstrip transmission line feeding technique

and for SW-TL feeding method, and the experimental

results for SW-TL feeding method a

in x-y plane.

in x-y plane. b

in x-z plane. b

in x-z plane.

in y-z plane. c

in y-z plane ..................... 53

Fig. 5.1 Meander SW-TL. a The schematic of the design. Inset:

the meander SSP cell. b Scattering parameter results

from the meander SW-TL

.............................. 58

Fig. 5.2 Radiation from the SW-TL. a Dispersion curves for the

dominant mode and the ﬁrst space harmonic. b Normalized

co-component ( u) radiation patterns of the SL-LWA in the y-z

plane at frequencies. c 3D radiation pattern at 17 GHz

........ 59

Fig. 5.3 Designed SL-SW-TL. a SL-LWA without the second

converter. b The magnetic ﬁeld distribution near

the SL-LWA

........................................ 61

Fig. 5.4 Effects of the 2nd mode converter. a The reﬂection spectrum,

b the maximum radiation direction and the gain

............. 61

Fig. 5.5 Dielectric substrate effect of SL-SW-TL. a The scattering

parameter results. b The maximum radiation angle

and the gain

........................................ 62

Fig. 5.6 Efﬁciency of SL-LWA. a Total efﬁciency with and without

the dielectric substrate. b The Radiation efﬁciency for three

cases: SL-LWA (1) with lossy metal and dielectric,

(2) with lossless dielectric and (3) with PEC

................ 62

Fig. 5.7 Effect of the loss on SL-LWA. The normalized decay

rate of the SL-LWA

.................................. 63

xxii List of Figures

Fig. 5.8 A simple strip antenna without grooves. a The schematic.

b The reﬂection results for varying geometrical parameters

.... 64

Fig. 5.9 Effect of the period length on SL-LWA. a The reﬂection and

b the maximum radiation angle with the varying

period lengths

....................................... 66

Fig. 5.10 Realized gain of SL-LWA. The maximum realized gain

in the y-z plane with varying a d and w. b Nm and l

c The broadside realized gain

........................... 67

Fig. 5.11 Experimental evaluation of SL-LWA. a The fabricated

prototype. b The measured reﬂection spectrum compared

with the simulation results

.............................. 68

Fig. 5.12 Normalized radiation pattern of SL-LWA. Comparison

between the measured and simulated results for the

co-component (u) as well as cross-component (h)

in the y-z plane at a 10.5, b 17, c 20 and d 24 GHz.

......... 69

Fig. 5.13 Maximum realized gain in y-z plane

...................... 69

Fig. A.1 TE-dominant higher order modes excited by SW-TL. The axial

component of the magnetic ﬁeld for EH

11d

), EH

21d

) and

31d

). The electric ﬁeld vectors for EH

11d

), EH

21d

)

and EH

31d

). The far ﬁeld radiation pattern of the

co-polarized component of the electric ﬁelds at the x-y-plane

for EH

11d

), EH

21d

) and EH

31d

). The resonance

frequency of each mode for the isolated DRA (value in

parentheses) as wel l as the DRA fed by SW-TL

(value out of parentheses) are indicated in (a

–a

)

in unit of GHz

....................................... 78

Fig. B.1 Normalized radiation pattern of SL-LWA.

Comparison between the measured and sim ulated results

for the co-component (u) as well as cross-component (h)

in the y-z plane at a 10.5, b 11, c 12, and d 13 GHz

......... 81

Fig. B.2 Normalized radiation pattern of SL-LWA. Comparison

between the measured and simulated results

for the co-component (u) as well as cross-component (h)

in the y-z plane at a 14, b 15, c 16, d 17, e 18, f 19,

g 20 and h 21 GHz

................................... 82

Fig. B.3 Normalized radiation pattern of SL-LWA. Comparison

between the measured and simulated results for the

co-component (u) as well as cross-component (h)

in the y-z plane at a 22, b 23, c 24, and d 24.5 GHz

......... 83

List of Figures xxiii

剩余96页未读，继续阅读

hanzhenru

粉丝: 2
资源: 7

超材料表面等离子体传输线与天线设计

CST studio suite 2016破解包以及详细安装和破解说明

等幅线性相位天线阵MATLAB小程序

基于原子范数的宽带压缩频谱感知研究_硕士论文_许康

Odd-Mode Surface Plasmon Polaritons Supported by Complementary Plasmonic Metamaterial

Theoretical and experimental study of the backward-wave radiation using resonant-type metamaterial transmission lines

Robust switch ef fect based on surface plasmon resonance in magnetic metamaterials

Low-loss Airy surface plasmon polaritons

Tunable terahertz absorber based on transparent and flexible metamaterial

Complementary metamaterial transmission line for monoband and dual‐band bandpass filters application

HFSS Metamaterial超材料仿真

最新资源