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PLL Design--Analysis of a Sigma-Delta Modulator Using RF Behavioral Modeling and System Simulation
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PLL Design--Analysis of a Sigma-Delta Modulator
Using RF Behavioral Modeling and System Simulation
© Copyright 2002 Agilent Technologies
All Right Reserved
1
Advanced RFIC Design Techniques
Phase Locked Loop Design--
Analysis of a Sigma-Delta Modulator Using RF
Behavioral Modeling and System Simulation
by Andy Howard
Applications Engineer
Welcome to this presentation. It is designed to give you an understanding of:
• Advanced Design System (ADS) and RF Design Environment (RFDE) Phase-
locked loop (PLL) simulation capabilities.
• PLL component behavioral modeling in Agilent ADS and RFDE
• Agilent ADS and RFDE post-processing capabilities
PLL Design--Analysis of a Sigma-Delta Modulator
Using RF Behavioral Modeling and System Simulation
© Copyright 2002 Agilent Technologies
All Right Reserved
2
Page 2
Introduction
• Agilent ADS and RFDE capabilities for simulating
PLLs
• PLL component behavioral modeling
• Agilent ADS and RFDE post-processing capabilities
PLL Design--Analysis of a Sigma-Delta Modulator
Using RF Behavioral Modeling and System Simulation
© Copyright 2002 Agilent Technologies
All Right Reserved
3
Page 3
Outline
• Basic phase-locked loop (PLL) operation
• Fractional-N PLL operation and simulation
• Behavioral modeling of a phase/frequency detector
• Simulating jitter in a transistor-level PFD and charge
pump
• Behavioral modeling of a VCO/divide-by-N
• Modeling an accumulator with Ptolemy
• Sigma-delta modulators
• Simulating a PLL with a sigma-delta modulator
• Adding phase noise to the VCO
PLL Design--Analysis of a Sigma-Delta Modulator
Using RF Behavioral Modeling and System Simulation
© Copyright 2002 Agilent Technologies
All Right Reserved
4
Page 4
Basic Phase-Locked Loop
In steady-state,
F
VCO
=N*F
REF
This phase-locked loop consists of a reference source, phase/frequency detector,
charge pump, loop filter, VCO, and divider. If the divide ratio is a constant, then the
loop will operate to force the VCO signal frequency to be exactly N times the
reference signal frequency. The phase/frequency detector and charge pump act to
output either positive or negative charge “pulses” depending on whether the
reference signal phase leads or lags the divided VCO signal phase. These charge
pulses are integrated by the loop filter to generate a tuning voltage. The tuning
voltage forces the VCO frequency up or down, such that the reference signal and
divided signal phases are synchronized.
Phase-locked loops are used as frequency synthesizers in many applications, where it
is necessary to generate a precise signal frequency with low spurs and good phase
noise. A VCO’s signal frequency can be changed by varying the reference signal
frequency or the divide ratio. Often, the reference signal is a very stable oscillator
whose frequency cannot be varied. So the divide ratio is changed in integer steps to
change the VCO frequency.
PLL Design--Analysis of a Sigma-Delta Modulator
Using RF Behavioral Modeling and System Simulation
© Copyright 2002 Agilent Technologies
All Right Reserved
5
Page 5
Problem with Basic Phase-Locked Loop
N can only have integer values, so
F
VCO
=…, (N-2)* F
REF
, (N-1)* F
REF
, N* F
REF
, (N+1)* F
REF
, …
The smallest frequency change in F
VCO
that can be made is
1*F
REF
What if you need finer frequency resolution?
One limitation with this type of phase-locked loop is that the VCO frequency cannot
be varied in steps any smaller than the reference frequency. (Although you could put
a 1/M divider between the reference signal and the phase/frequency detector, in
which case the VCO output frequency would be N*Fref/M.) Due to mismatches in
the PLL’s charge pump and other factors such as the non-ideal behavior of
phase/frequency detectors, even when the loop is locked, the charge pump still
outputs small charge pulses which cause sidebands or spurs to appear in the VCO
output spectrum, at offset frequencies equal to the reference frequency. So, for fine
frequency resolution, you want a small reference frequency. But this will cause
spurs to be generated at a smaller offset frequency from the VCO, meaning they will
require that a narrower loop filter bandwidth be used to filter them. PLLs with
narrower loop bandwidths have longer transient settling times (the time required to
transition from one frequency to another) and such loops may not operate at the
required speed. Reference 1 has a discussion of PLL settling time requirements.
Also, the narrower the PLL’s loop bandwidth, the less the VCO’s phase noise is
supressed.
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