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MIMO-OQAM/FBMC信道估计:FDM结构前导码优化减小MSE
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更新于2024-08-27
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本文主要探讨了在多输入多输出(MIMO)系统中,基于正交正交幅度调制(OQAM)和滤波器组多载波(FBMC)技术的频分复用(FDM)结构化前同步码优化方法。针对信道估计的准确性,作者提出了一个优化问题,目标是减小信道估计的均方误差(MSE),这是无线通信系统中衡量接收信号质量的重要指标。 在双天线(即两个发射天线)的情景下,研究者发现了前同步码与邻近符号的本征干扰之间存在关键关系,通过优化这种关系,能够实现最小化的MSE。这个优化过程得到了一个闭式解,这意味着可以直接计算出最优的前同步码结构,无需迭代求解,从而节省了计算资源。 当系统扩展到三个或更多天线时,优化问题变得更为复杂,原有的优化问题被转化为二次约束二次规划问题。由于原问题的某些约束是非凸的,解决起来较为困难。为了找到可行的次优解,研究者选择放宽这些非凸约束,通过数值仿真来验证这种方法的有效性。 实验结果显示,相较于传统的FDM方法,这种优化后的前同步码策略在各种信噪比(SNR)条件下都能提升信道估计的精度和降低误码率。尤其是在中低SNR环境下,优化方法的表现优于那些依赖于复杂干扰模型的近似方法,同时降低了前导码开销,提高了系统的整体效率和可靠性。 总结来说,这篇论文提供了对MIMO-OQAM/FBMC系统中FDM结构化前导码优化的一种有效策略,对于提高无线通信系统的性能,特别是在多天线环境下的信号处理和信道估计有着重要的实际应用价值。
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LIU et al.: FDM-STRUCTURED PREAMBLE OPTIMIZATION FOR CHANNEL ESTIMATION IN MIMO-OQAM/FBMC SYSTEMS 8435
Fig. 1. The MIMO-OQAM/FBMC system model.
with ja
(i)
m,n
being the intrinsic imaginary interference from the
neighboring frequency-time (FT) points. With a well localized
pulse g[k] in time and frequency, it can be assumed that the
intrinsic imaginary interference mostly originates from the
first-order neighboring FT points [34]. Let us denote
ζ
p,q
m,n
=
∞
k=−∞
g
m,n
[k]g
∗
p,q
[k]. (3)
Then, the imaginary interference term ja
(i)
m,n
can be approxi-
mated as
ja
(i)
m,n
≈
(p
0
,q
0
)∈Ω
1
a
m+p
0
,n+q
0
ζ
m,n
m+p
0
,n+q
0
, (4)
where the neighborhood Ω
1
= {(p
0
,q
0
)| p
0
, q
0
∈{−1,
0, 1} and (p
0
,q
0
) =(0, 0)} and ζ
m,n
m+p
0
,n+q
0
represents the
contribution of a
m+p
0
,n+q
0
to the imaginary interference
ja
(i)
m,n
. It is noteworthy that for a well-designed prototype filter
g[k], ζ
m,n
m+p
0
,n+q
0
is pure imaginary for any (p
0
,q
0
) =(0, 0)
and ζ
m,n
m+p
0
,n+q
0
=1for (p
0
,q
0
)=(0, 0). Thus, for (p
0
,q
0
) =
(0, 0), in the remainder of this paper, we refer to the terms
ζ
m,n
m+p
0
,n+q
0
as the imaginary interference coefficients.
Note that, the intrinsic imaginary interference could be
removed by taking the real part after channel equalization.
In this paper, since we mainly focus on the preamble design
issues, the equalization and operation of taking real part are
not discussed.
B. MIMO-OQAM/FBMC System Model
The MIMO-OQAM/FBMC system model is depicted
in Fig. 1, where the transmitter and the receiver are equipped
with N
t
and N
r
antennas, respectively. Since the channel esti-
mation performance of MIMO-OQAM/FBMC systems would
not differ in the case of channel coding, we only consider the
uncoded scenario below.
At the transmitter side, the symbols spatially multiplexed
on the mth subcarrier at the nth time index are denoted by
a
m,n
=
a
1
m,n
,a
2
m,n
, ··· ,a
N
t
m,n
T
, each element of which
is transmitted at different antennas after the corresponding
OQAM/FBMC modulation. At the receiver side, the link
of each transmit and receive antenna pair is degraded by
multipath fading and contaminated with AWGN. For each
given FT position (m, n),letH
r,t
m
be the frequency response
of the channel between the tth transmit antenna and the rth
receive antenna and η
r
m,n
be the noise component at the
rth receive antenna. By assuming perfect time and frequency
synchronization, the demodulated symbol of the rth receive
antenna can be obtained by extending (2) to the MIMO case
as [16], [20]
y
r
m,n
=
N
t
t=1
H
r,t
m
c
t
m,n
+ η
r
m,n
, 1 ≤ r ≤ N
r
, (5)
where c
t
m,n
represents the corresponding virtually transmitted
symbol at the tth transmit antenna. According to (4), c
t
m,n
can
be written as
c
t
m,n
= a
t
m,n
+
(p
0
,q
0
)∈Ω
1
a
t
m+p
0
,n+q
0
ζ
m,n
m+p
0
,n+q
0
, 1 ≤ t ≤ N
t
.
(6)
We denote the demodulated symbol vector by y
m,n
=
y
1
m,n
,y
2
m,n
, ··· ,y
N
r
m,n
T
, the virtually transmitted vector by
c
m,n
=
c
1
m,n
,c
2
m,n
, ··· ,c
N
t
m,n
T
and the additive noise vector
by η
m,n
=
η
1
m,n
,η
2
m,n
, ··· ,η
N
r
m,n
T
. Thus, the equation (5)
can be expressed as
y
m,n
= H
m
c
m,n
+ η
m,n
, (7)
where
H
m
=
⎡
⎢
⎢
⎢
⎣
H
1,1
m
H
1,2
m
··· H
1,N
t
m
H
2,1
m
H
2,2
m
··· H
2,N
t
m
.
.
.
.
.
.
.
.
.
.
.
.
H
N
r
,1
m
H
N
r
,2
m
··· H
N
r
,N
t
m
⎤
⎥
⎥
⎥
⎦
(8)
is the MIMO channel frequency response (CFR) at that FT
point.
III. T
HE CONVENTIONAL PREAMBLE DESIGN METHODS
IN
MIMO-OQAM/FBMC SYSTEMS
Since the orthogonality condition of the OQAM/FBMC
system only holds in the real field, which causes intrinsic
imaginary interference to preamble symbols at the receiver,
preamble design in the OQAM/FBMC system is more difficult
than that in OFDM. Worse is that there also exists multi-
antenna interference when OQAM/FBMC is extended to the
MIMO case. In this section, we tackle the preamble design
problem in MIMO-OQAM/FBMC systems and give a brief
review of the conventional preamble design methods.
A. IAM Method
IAM preamble design method has drawn much attention
due to its simplicity and efficiency [20]. The IAM family
that includes IAM-R, IAM-imaginary (IAM-I), IAM-C, and
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