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首页第五版《自适应滤波原理》英文课后习题答案
《自适应滤波器原理(第五版)》英文版课后答案解析,由Simon Haykin和Kelvin Hall两位作者共同创作,他们是加拿大麦克马斯特大学的学者。本书是针对赫金教授的经典教材,专门探讨自适应滤波器的理论与实践。这本Solution Manual涵盖了第五版的所有章节,旨在帮助学生理解和解决书中习题,深入理解自适应滤波器的设计、学习算法如Least Mean Squares (LMS)和Levenberg-Marquardt Backpropagation (LMBP)等。 书中特别提到了对复杂数据处理的Wirtiger Calculus的支持,这是由马里兰大学的Tulai Adali教授引入的,它在处理部分微分问题时具有重要作用。Ashique Rupam Mahomood博士也贡献了大量计算机实验,尤其是在第十三章中应用AutoStep方法及其解决方案,以及该章末尾的相关问题,他的帮助使读者能够通过实际操作加深理解。 Erkan Baser的研究生项目也被收录在附录中,该项目回顾了第六章关于LMS算法的自适应均衡实验,但这次使用的是IDB算法。这部分不仅展示了理论在实际项目中的应用,也提供了实际问题求解的实例,有助于学生掌握如何在实际环境中设计和优化自适应滤波器。 这本Solution Manual不仅是学习者解决作业难题的宝贵工具,还包含了作者们对自适应滤波技术不断探索和发展的最新成果,对于那些希望在信号处理、通信工程或机器学习领域深入研究的读者来说,是一份不可多得的学习资料。无论是理论概念的理解还是实践经验的积累,都能从中获益匪浅。
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PROBLEM 1.9. CHAPTER 1.
Equivalently, except for the scaling factor r(0),
{a
1
, a
2
, . . . , a
M
} {r(1), r(2), . . . , r(M)} (2)
Combining Equation (1) and Equation (2):
{P
0
, a
1
, a
2
, . . . , a
M
} {r(0), r(1), r(2), . . . , r(M)} (3)
Problem 1.9
a)
The transfer function of the MA model of Fig. 1.3 is
H(z) = 1 + b
∗
1
z
−1
+ b
∗
2
z
−2
+ . . . + b
∗
K
z
−K
b)
The transfer function of the ARMA model of Fig. 1.4 is
H(z) =
b
0
+ b
∗
1
z
−1
+ b
∗
2
z
−2
+ . . . + b
∗
K
z
−K
1 + a
∗
1
z
−1
+ a
∗
2
z
−2
+ . . . + a
∗
M
z
−M
c)
The ARMA model reduces to an AR model when
b
0
= b
1
= . . . = b
K
= 0
The ARMA model reduces to MA model when
a
1
= a
2
= . . . = a
M
= 0
10
PROBLEM 1.10. CHAPTER 1.
Problem 1.10
∗
Taking the z-transform of both sides of the correct equation:
X(z) = (1 + 0.75z
−1
+ 0.25z
−2
)V (z)
Hence, the transfer function of the MA model is:
X(z)
V (z)
=1 + 0.75z
−1
+ 0.75z
−1
=
1
(1 + 0.75z
−1
+ 0.75z
−1
)
−1
(1)
Using long division we may perform the following expansion of the denominator in Equa-
tion (1):
(1 + 0.75z
−1
+ 0.75z
−1
)
−1
= 1 −
3
4
z
−1
+
5
16
z
−2
−
3
64
z
−3
−
11
256
z
−4
−
45
1024
z
−5
−
91
4096
z
−6
+
93
16283
z
−7
−
85
65536
z
−8
−
627
262144
z
−9
+
1541
1048576
z
−10
+ . . .
≈ 1 − 0.75z
−1
+ 0.3125z
−2
− 0.0469z
−3
− 0.043z
−4
− 0.0439z
−5
− 0.0222z
−6
+ 0.0057z
−7
− 0.0013z
−8
− 0.0024z
−9
+ 0.0015z
−10
(2)
a)
M = 2
Retaining terms in Equation (2) up to z
−2
, we may approximate the MA model with an
AR model of order two as follows:
X(z)
V (z)
≈
1
1 − 0.75z
−1
+ 0.3125z
−2
∗
Correction: the question was meant to ask the reader to consider an MA process x(n) of order two
described by the difference equation
x(n) = ν(n) + 0.75ν(n − 1) + 0.25ν(n − 2)
not the equation
x(n) = ν(n) + 0.75ν(n − 1) + 0.75ν(n − 2)
11
PROBLEM 1.11. CHAPTER 1.
b)
M = 5
Retaining terms in Equation (2) up to z
−5
, we may approximate the MA model with an
AR model of order two as follows:
X(z)
V (z)
≈
1
1 − 0.75z
−1
+ 0.3125z
−2
− 0.0469z
−3
− 0.043z
−4
+ 0.0439z
−5
c)
M = 10
Retaining terms in Equation (2) up to z
−10
, we may approximate the MA model with an
AR model of order two as follows:
X(z)
V (z)
≈
1
D(z)
where D(z) is given by the polynomial on the right-hand side of Equation (2).
Problem 1.11
a)
The filter output is
x(n) = w
H
u(n)
where u(n) is the tap-input vector. The average power of the filter output is therefore
E[|x(n)|
2
] = E[w
H
u(n)u
H
(n)w]
= w
H
E[u(n)u
H
(n)]w
= w
H
Rw
b)
If u(n) is extracted from a zero-mean white noise with variance σ
2
, then
R = σ
2
I
where I is the identity matrix. Hence,
E[|x(n)|
2
] = σ
2
w
H
w
12
PROBLEM 1.12. CHAPTER 1.
Problem 1.12
a)
The process u(n) is a linear combination of Gaussian samples. Hence, u(n) is Gaussian.
b)
From inverse filtering, we recognize that ν(n) may also be expressed as a linear combina-
tion of samples relating to u(n). Hence, if u(n) is Gaussian, then ν(n) is also Gaussian.
Problem 1.13
a)
From the Gaussian moment factoring theorem:
E[(u
∗
1
u
2
)
k
] =E[u
∗
1
. . . u
∗
1
u
2
. . . u
2
]
=k!E[u
∗
1
u
2
] . . . E[u
∗
1
u
2
]
=k!(E[u
∗
1
u
2
])
k
(1)
b)
By allowing u
2
= u
1
= u, Equation (1) reduces to:
E[|u|
2k
] = k!(E[|u|
2
])
k
Problem 1.14
It is not permissible to interchange the order of expectation and limiting operation in Equa-
tion (1.113). The reason is that the expectation is a linear operation, whereas the limiting
operation with respect to the number of samples N is nonlinear.
Problem 1.15
The filter output is
y(n) =
X
i
h(i)u(n − i)
13
PROBLEM 1.16. CHAPTER 1.
Similarly, we may write
y(m) =
X
k
h(k)u(m − k)
Hence,
r
y
(n, m) = E[y(n)y
∗
(m)]
= E
"
X
i
h(i)u(n − i)
X
k
h
∗
(k)u
∗
(m − k)
#
=
X
i
X
k
h(i)h
∗
(k)E [u(n − i)u
∗
(m − k)]
=
X
i
X
k
h(i)h
∗
(k)r
u
(n − i, m − k)
Problem 1.16
The mean-square value of the filter output response to white noise input is
P
0
=
2σ
2
∆ω
π
The value P
0
is linearly proportional to the filter bandwidth ∆ω. This relation holds irre-
spective of how small ∆ω is compared to the mid-band frequency of the filter.
Problem 1.17
a)
The variance of the filter output is
σ
2
y
=
2σ
2
∆ω
π
It has been stated that
σ
2
= 0.1 volts
2
14
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